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LT6105 1 6105f typical application features applications description precision, extended input range current sense ampli er the lt ? 6105 is a micropower, precision current sense ampli? er with a very wide input common mode range. the LT6105 monitors unidirectional current via the volt- age across an external sense resistor. the input common mode range extends from C0.3v to 44v, with respect to the negative supply voltage (v C ). this allows the LT6105 to operate as a high side current sense monitor or a low side current sense monitor. it also allows the LT6105 to monitor current on a negative supply voltage, as well as continuously monitor a battery from full charge to depletion. the inputs of LT6105 can withstand differential voltages up to 44v, which makes it ideal for monitoring a fuse or mosfet switch. gain is con? gured with external resistors from 1v/v to 100v/v. the input common mode rejection and power supply rejection are in excess of 100db and the input offset voltage is less than 300v. a minimum slew rate of 2v/s ensures fast response to unexpected current changes. the LT6105 can operate from an independent power supply of 2.85v to 36v and draws only 150a. when v + is powered down, the sense pins are biased off. this prevents loading of the monitored circuit, irrespective of the sense voltage. the LT6105 is available in a 6-lead dfn and 8-lead msop package. gain error vs input voltage n very wide, over-the-top ? , input common mode range - extends 44v above v C (independent of v + ) - extends C0.3v below v C n wide power supply range: 2.85v to 36v n input offset voltage: 300v maximum n gain accuracy: 1% max n gain con? gurable with external resistors n operating current: 150a n slew rate: 2v/s n sense input current when powered down: 1na n full-scale output current: 1ma minimum n operating temperature range C40c to 125c n available in 2mm 3mm dfn and 8-lead msop packages n high side or low side current sensing n current monitoring on positive or negative supply voltages n battery monitoring n fuse/mosfet monitoring n automotive n power management n portable test/measurement systems gain of 50 current sense ampli? er C + 0.02 r in2 100 r in1 100 r out 4.99k LT6105 2.85v to 36v to load source C0.3v to 44v v out = 1v/a v out v + v C v s + v s C Cin +in 6105 ta01 vvv r r a r r rr out s s out in v out in in in =? () == +? ?; ; 12 = = r in , lt, ltc, ltm and over-the-top are registered trademarks of linear technology corporation. all other trademarks are the property of their respective owners. v s + input voltage (v) 0 gain error (%) 2 3 35 1 0 10 20 5 15 25 40 30 45 C3 C4 C1 4 C2 6105 ta01b t a = 25c t a = 85c t a = 125c v + = 12v v sense = 50mv r in = 100 a v = 50v t a = C 40c
LT6105 2 6105f absolute maximum ratings differential input voltage (+in ? ?in) .....................44v input voltage v(+in, ?in) to v ? ................ ?9.5v to 44v total v + supply voltage from v ? ...............................36v output voltage ......................................v ? to (v ? + 36v) output short-circuit duration (note 3) ............ inde? nite operating temperature range (note 4) LT6105c ...............................................?40c to 85c LT6105i ................................................?40c to 85c LT6105h ............................................?40c to 125c (notes 1, 2) top view +in nc v out ?in v + v ? dcb package 6-lead (2mm 3mm) plastic dfn 4 5 7 6 3 2 1 t jmax = 150c, ja = 64c/w exposed pad (pin 7) connected to v ? (pin 3) 1 2 3 4 ?in v + nc v ? 8 7 6 5 +in nc nc v out top view ms8 package 8-lead plastic msop t jmax = 150c, ja = 250c/w pin configuration order information lead free finish tape and reel part marking* package description specified temperature range LT6105cdcb#trmpbf LT6105idcb#trmpbf LT6105hdcb#trmpbf LT6105cdcb#trpbf LT6105idcb#trpbf LT6105hdcb#trpbf lctf lctf lctf 6-lead (2mm 3mm) plastic dfn 6-lead (2mm 3mm) plastic dfn 6-lead (2mm 3mm) plastic dfn 0c to 70c ?40c to 85c ?40c to 125c LT6105cms8#pbf LT6105ims8#pbf LT6105hms8#pbf LT6105cms8#trpbf LT6105ims8#trpbf LT6105hms8#trpbf lt c t d lt c t d lt c t d 8-lead plastic ms8 8-lead plastic ms8 8-lead plastic ms8 0c to 70c ?40c to 85c ?40c to 125c trm = 500 pieces. *temperature grades are identi? ed by a label on the shipping container. consult ltc marketing for parts speci? ed with wider operating temperature ranges. *the temperature grade is identi? ed by a label on the shipping container. consult ltc marketing for parts speci? ed with wider operating temperature ranges. for more information on lead free part marking, go to: http://www.linear.com/leadfree/ for more information on tape and reel speci? cations, go to: http://www.linear.com/tapeandreel/ speci? ed temperature range (note 5) LT6105c ................................................... 0c to 70c LT6105i ................................................?40c to 85c LT6105h ............................................?40c to 125c maximum junction temperature........................... 150c storage temperature range ...................?65c to 150c lead temperature (soldering, 10 sec) msop ............................................................... 300c
LT6105 3 6105f electrical characteristics symbol parameter conditions min typ max units v s + , v s C input voltage range guaranteed by cmrr l C0.3 C0.1 44 44 v v a v error voltage gain error (note 6) v sense = 25mv to 75mv, v s + = 12v l C1 C1.3 0.1 1 1.3 % % v sense = 25mv to 75mv, v s + = 0v l C2.5 2.5 % v os input offset voltage ms8 package v sense = 5mv l C0.3 C0.6 C0.1 0.3 0.6 mv mv input offset voltage dcb package v sense = 5mv l C0.4 C0.7 C0.1 0.4 0.7 mv mv input offset voltage v sense = 5mv, v s + = 0v l C1 C1.3 C0.3 1 1.3 mv mv v os / t temperature coef? cient of v os l 0.5 v/c cmrr input common mode rejection ratio v sense = 5mv, v s + = 2.8v to 44v l 100 95 120 db db v sense = 5mv, v s + = C0.3v to 44v v sense = 5mv, v s + = C0.1v to 44v l 94 90 db db v + power supply voltage range guaranteed by psrr l 2.85 36 v psrr power supply rejection ratio v sense = 5mv, v s + = 12v, v + = 2.85v to 36v l 98 94 120 db db v sense = 5mv, v s + = 0v, v + = 2.85v to 36v l 98 94 120 db db i (+in) , i (Cin) input current v sense = 0v, v s + = 3v v sense = 0v, v s + = 0v l l 15 C0.05 25 a a i (+in) C i (Cin) input offset current v sense = 0v, v s + = 3v v sense = 0v, v s + = 0v l l 0.05 0.005 0.5 a a i (+in) + i (Cin) input current (power-down) v + = 0v, v s + = 44v, v sense = 0v l 0.03 1 a i s v + supply current v sense = 0v, v s + = 3v, v + = 2.85v v sense = 0v, v s + = 3v, v + = 36v l l 200 240 300 350 a a v o(min) minimum output voltage v sense = 0mv, v s + = 44v, v + = 36v l 35 mv v o(max) output high (referred to v + )v sense = 120mv, a v = 100, r l = 10k l 1.25 1.5 v i out maximum output current guaranteed by v o(max) l 1ma i sc short-circuit output current v s + = 44v, v s C = 0v, r out = 0 l 1.5 ma bw C3db bandwidth v sense = 50mv, a v = 10v/v 100 khz t s output settling to 1% of final value v sense = 5mv to 100mv 5 s t r input step response (note 7) v sense = 5mv to 100mv 3 s sr slew rate (note 8) v sense = 5mv to 150mv, a v = 50v/v, r in = 400 1.75 2.25 v/s v rev reverse input voltage (referred to v C ) i (+in) + i (Cin) = C5ma l C9.5 C12 v the l denotes the speci? cations which apply over the temperature range 0c < t a < 70c (LT6105c), otherwise speci? cations are at t a = 25c. v + = 12v, v C = 0v, v s + = 12v (see figure 1), r in1 = r in2 = 100 , r out = 5k (a v = 50), v sense = v s + C v s C , unless otherwise speci? ed. (note 5)
LT6105 4 6105f electrical characteristics the l denotes the speci? cations which apply over the temperature range C40c < t a < 85c (LT6105i), otherwise speci? cations are at t a = 25c. v + = 12v, v C = 0v, v s + = 12v (see figure 1), r in1 = r in2 = 100 , r out = 5k (a v = 50), v sense = v s + C v s C , unless otherwise speci? ed. (note 5) symbol parameter conditions min typ max units v s + , v s C input voltage range guaranteed by cmrr l C0.3 C0.3 44 44 v v a v error voltage gain error (note 6) v sense = 25mv to 75mv, v s + = 12v l C1 C1.4 0.1 1 1.4 % % v sense = 25mv to 75mv, v s + = 0v l C3 3 % v os input offset voltage ms8 package v sense = 5mv l C0.3 C0.65 C0.1 0.3 0.65 mv mv input offset voltage dcb package v sense = 5mv l C0.4 C0.75 C0.1 0.4 0.75 mv mv input offset voltage v sense = 5mv, v s + = 0v l C1 C1.4 C0.3 1 1.4 mv mv v os / t temperature coef? cient of v os l 0.5 v/c cmrr input common mode rejection ratio v sense = 5mv, v s + = 2.8v to 44v l 100 95 120 db db v sense = 5mv, v s + = C0.3v to 44v v sense = 5mv, v s + = C0.1v to 44v l 94 90 db db v + power supply voltage range guaranteed by psrr l 2.85 36 v psrr power supply rejection ratio v sense = 5mv, v s + = 12v, v + = 2.85v to 36v l 98 94 120 db db v sense = 5mv, v s + = 0v, v + = 2.85v to 36v l 98 94 120 db db i (+in) , i (Cin) input current v sense = 0v, v s + = 3v v sense = 0v, v s + = 0v l l 16 C0.05 27 a a i (+in) C i (Cin) input offset current v sense = 0v, v s + = 3v v sense = 0v, v s + = 0v l l 0.08 0.01 0.6 a a i (+in) + i (Cin) input current (power-down) v + = 0v, v s + = 44v, v sense = 0v l 0.035 1 a i s v + supply current v sense = 0v, v s + = 3v, v + = 2.85v v sense = 0v, v s + = 3v, v + = 36v l l 200 250 325 375 a a v o(min) minimum output voltage v sense = 0mv, v s + = 44v, v + = 36v l 40 mv v o(max) output high (referred to v + )v sense = 120mv, a v = 100, r l = 10k l 1.27 1.6 v i out maximum output current guaranteed by v o(max) l 1ma i sc short-circuit output current v s + = 44v, v s C = 0v, r out = 0 l 1.5 ma bw C3db bandwidth v sense = 50mv, a v = 10v/v 100 khz t s output settling to 1% of final value v sense = 5mv to 100mv 5 s t r input step response (note 7) v sense = 5mv to 100mv 3 s sr slew rate (note 8) v sense = 5mv to 150mv, a v = 50v/v, r in = 400 1.75 2.25 v/s v rev reverse input voltage (referred to v C ) i (+in) + i (Cin) = C5ma l C9.25 C12 v
LT6105 5 6105f electrical characteristics the l denotes the speci? cations which apply over the temperature range C40c < t a < 125c (LT6105h), otherwise speci? cations are at t a = 25c. v + = 12v, v C = 0v, v s + = 12v (see figure 1), r in1 = r in2 = 100 , r out = 5k (a v = 50), v sense = v s + C v s C , unless otherwise speci? ed. (note 5) symbol parameter conditions min typ max units v s + , v s C input voltage range guaranteed by cmrr l C0.3 C0.1 44 44 v v a v error voltage gain error (note 6) v sense = 25mv to 75mv, v s + = 12v l C1 C1.5 0.1 1 1.5 % % v sense = 25mv to 75mv, v s + = 0v l C3.25 3.25 % v os input offset voltage ms8 package v sense = 5mv l C0.3 C0.8 C0.1 0.3 0.8 mv mv input offset voltage dcb package v sense = 5mv l C0.4 C0.9 C0.1 0.4 0.9 mv mv input offset voltage v sense = 5mv, v s + = 0v l C1 C1.6 C0.3 1 1.6 mv mv v os / t temperature coef? cient of v os l 0.5 v/c cmrr input common mode rejection ratio v sense = 5mv, v s + = 2.8v to 44v l 100 95 120 db db v sense = 5mv, v s + = C0.3v to 44v v sense = 5mv, v s + = C0.1v to 44v l 94 80 db db v + power supply voltage range guaranteed by psrr l 2.85 36 v psrr power supply rejection ratio v sense = 5mv, v s + = 12v, v + = 2.85v to 36v l 98 94 120 db db v sense = 5mv, v s + = 0v, v + = 2.85v to 36v l 98 94 120 db db i (+in) , i (Cin) input current v sense = 0v, v s + = 3v v sense = 0v, v s + = 0v l l 18 C0.05 30 a a i (+in) C i (Cin) input offset current v sense = 0v, v s + = 3v v sense = 0v, v s + = 0v l l 0.35 0.1 0.8 a a i (+in) + i (Cin) input current (power-down) v + = 0v, v s + = 44v, v sense = 0v l 0.5 2.5 a i s v + supply current v sense = 0v, v s + = 3v, v + = 2.85v v sense = 0v, v s + = 3v, v + = 36v l l 240 300 350 450 a a v o(min) minimum output voltage v sense = 0mv, v s + = 44v, v + = 36v l 45 mv v o(max) output high (referred to v + )v sense = 120mv, a v = 100, r l = 10k l 1.3 1.7 v i out maximum output current guaranteed by v o(max) l 1ma i sc short-circuit output current v s + = 44v, v s C = 0v, r out = 0 l 1.5 ma bw C3db bandwidth v sense = 50mv, a v = 10v/v 100 khz t s output settling to 1% of final value v sense = 5mv to 100mv 5 s t r input step response (note 7) v sense = 5mv to 100mv 3 s sr slew rate (note 8) v sense = 5mv to 150mv, a v = 50v/v, r in = 400 1.75 2.25 v/s v rev reverse input voltage (referred to v C ) i (+in) + i (Cin) = C5ma l C9 C12 v
LT6105 6 6105f v s + input voltage (v) 0 input offset voltage (mv) 0.20 0.40 0.60 35 0 C0.20 10 20 5 15 25 40 30 45 C0.80 C1.00 C0.40 0.80 C0.60 6105 g03 t a = C 40c t a = 25c t a = 85c t a = 125c v + = 12v v sense = 5mv a v = 50v/v typical performance characteristics input offset voltage vs temperature, v s + = 12v input offset voltage vs temperature, v s + = 0v input offset voltage vs input voltage input offset voltage vs supply voltage, v s + = 12v input offset voltage vs supply voltage, v s + = 0v gain error distribution, v s + = 12v note 1: stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. exposure to any absolute maximum rating condition for extended periods may affect device reliability and lifetime. note 2: esd (electrostatic discharge) sensitive devices. extensive use of esd protection devices are used internal to the LT6105, however, high electrostatic discharge can damage or degrade the device. use proper esd handling precautions. note 3: a heat sink may be required to keep the junction temperature below absolute maximum ratings. note 4: the LT6105c/LT6105i are guaranteed functional over the operating temperature range of C40c to 85c. the LT6105h is electrical characteristics guaranteed functional over the operating temperature range of C40c to 125c. note 5: the LT6105c is guaranteed to meet speci? ed performance from 0c to 70c. the LT6105c is designed, characterized and expected to meet speci? ed performance from C40c to 85c but is not tested or qa sampled at these temperatures. the LT6105i is guaranteed to meet speci? ed performance from C40c to 85c. the LT6105h is guaranteed to meet speci? ed performance from C40c to 125c. note 6: 0.01% tolerance external resistors are used. note 7: t r is measured from the input to the 2.5v point on the 5v output. note 8: slew rate is measured on the output between 1v and 5v. temperature (c) C40 input offset voltage (v) 100 200 300 65 0 C100 C10 20 C25 95 535 80 110 50 125 C300 C400 C200 400 6105 g01 v + = 12v v sense = 5mv typical units temperature (c) C40 input offset voltage (v) 0 400 800 65 C200 C400 C10 20 C25 95 535 80 110 50 125 C800 C1000 C600 200 600 1000 6105 g02 v + = 12v v sense = 5mv typical units v + supply voltage (v) 0 input offset voltage (mv) 0.2 0.6 0.0 0.4 35 C0.2 C0.4 10 20 5 15 25 30 40 C0.6 C0.8 0.8 6105 g04 v sense = 5mv t a = C40 c t a = 85 c t a = 125 c t a = 25 c v + supply voltage (v) 0 input offset voltage (mv) C0.2 0.0 35 C0.4 C0.6 10 20 5 15 25 40 30 C1.2 C1.4 C0.8 0.2 C1.0 6105 g05 t a = 25c t a = 85c t a = 125c v sense = 5mv t a = C 40c gain error (%) C0.5 percent of units (%) 25 30 35 0.2 20 15 C0.3 C0.1 C0.4 0.4 C0.2 0 0.3 0.1 0.5 5 0 10 40 6105 g06 v + = 12v v sense = 50mv r in = 100 a v = 50v/v 500 samples
LT6105 7 6105f temperature (c) C50 gain error (%) C25 0 50 25 75 100 125 6105 g09 C0.5 C0.3 C0.1 0.1 0.3 0.5 C0.4 C0.2 0.0 0.2 0.4 v + = 12v v sense = 50mv r in = 100 a v = 50v/v typical performance characteristics gain error distribution, v s + = 0v gain error vs input voltage gain error vs temperature, v s + = 12v gain error vs output resistance input referred voltage error vs v sense , v s + = 0v gain error vs temperature, v s + = 0v input referred voltage error vs v sense , v s + = 12v input bias current vs input voltage input current vs input voltage, v sense = 50mv v sense (mv) 0 C2 input referred error (mv) 0 20 40 80 60 100 2 C1 1 120 6105 g12 v + = 12v r in = 100 a v = 50v/v t a = C 40c t a = 25c t a = 85c t a = 125c v sense (mv) 0 input referred error (mv) 20 40 80 60 100 120 6105 g13 t a = C 40c C5.0 C3.0 C1.0 1.0 3.0 5.0 C4.0 C2.0 0.0 2.0 4.0 v + = 12v r in = 100 a v = 50v/v t a = 85c t a = 25c t a = 125c v s + input voltage (v) 0 C100.00 input bias current (a) C1.00 C0.01 0.01 0.5 1 1.5 2 2.5 1.00 100.00 C10.00 C0.10 0 0.1 10.00 3 6105 g14 v + = 3v v sense = 0v r in = 100 t a = C 40c t a = 125c t a = 85c t a = 25c v s + input voltage (v) 0 input current (ma) 1.0 1.5 35 0.5 0.0 10 20 5 15 25 40 30 45 C1.5 C2.0 C0.5 2.0 C1.0 6105 g15 i (+in) i (Cin) v + = 12v r in = 100 a v = 50v/v v s + input voltage (v) 0 gain error (%) 2 3 35 1 0 10 20 5 15 25 40 30 45 C3 C4 C1 4 C2 6105 g08 t a = 25c t a = 85c t a = 125c v + = 12v v sense = 50mv r in = 100 a v = 50v t a = C 40c gain error (%) C2.3 percent of units (%) 25 30 35 C1.6 20 15 C2.1 C1.9 C2.2 C2.0 C1.8 C1.5 C1.7 C1.4 5 0 10 45 40 6105 g07 v + = 12v v sense = 50mv r in = 100 a v = 50v/v 500 samples temperature (c) C4.0 gain error (%) C3.2 C2.4 C1.6 C0.8 0 C3.6 C2.8 C2.0 C1.2 C0.4 6105 g10 v + = 12v v sense = 50mv r in = 100 a v = 50v/v C50 C25 0 50 25 75 100 125 r out output resistance () 0 gain error (%) C2 3 4 5 6 2000 4000 6000 C4 1 C3 2 C5 C6 0 C1 8000 10000 6105 g11 v in = 12v v sense = 50mv r in = 100 a v = r out /r in v s + = 12v v s + = 0v
LT6105 8 6105f typical performance characteristics input current (v + powered down) vs input voltage output voltage vs v sense voltage, v s + = 12v output voltage vs v sense voltage, v s + = 0v output saturation voltage vs output current, v s + = 12v output saturation voltage vs output current, v s + = 0.5v supply current vs supply voltage, v s + = 12v output short-circuit current vs temperature supply current vs supply voltage, v s + = 0v v s + input voltage (v) input current (na) 5 101520253035404550 6105 g16 0 0.01 0.1 10 1 0.001 0.0001 100 1000 v + = 0v v sense = 0v t a = C40 c t a = 85 c t a = 125 c t a = 25 c v sense (mv) C10 10 30 50 output voltage (v) 0.8 1.2 0.4 0.0 70 90 110 130 1.6 0.6 1.0 0.2 1.4 6105 g17 v + = 3v r in = 100 a v = 10v/v t a = C 40c t a (25c, 85c, 125c) v sense (mv) C10 10 30 50 output voltage (v) 0.8 1.2 0.4 0.0 70 90 110 130 0.6 1.0 0.2 1.4 6105 g18 v + = 3v r in = 100 a v = 10v/v t a (C 40c, 25c, 85c, 125c) output current (ma) output saturati0n voltage (v) 0.001 0.10 1 10 0.01 6105 g19 1.5 1.7 1.9 1.4 1.3 1.1 1.0 1.2 1.6 1.8 2.0 v + = 12v v sense = 0.5v r in = 100 output saturation voltage = v + C v out t a = C 40c t a = 25c t a = 85c t a = 125c output current (ma) output saturati0n voltage (v) 0.001 0.10 1 10 0.01 6105 g20 0.9 1.1 1.3 0.8 0.7 0.5 0.4 0.6 1.0 1.2 1.4 output saturation voltage = v + C v out v + = 12v v sense = 0.5v r in = 100 t a = C 40c t a = 25c t a = 125c t a = 85c temperature (c) C40 output short-circuit current (ma) 2.8 3.0 3.2 65 2.6 2.4 C10 20 C25 95 535 80 110 50 125 2.2 2.0 3.4 6105 g21 v + = 5v v s + = 5v v sense = 5v r in = 100 v + supply voltage (v) 0 supply current (a) 35 400 10 20 5 15 25 40 30 100 0 300 500 200 6105 g22 v sense = 0v r in = 100 a v = 50v/v t a = C 40c t a = 25c t a = 85c t a = 125c v + supply voltage (v) 0 supply current (a) 35 400 10 20 5 15 25 40 30 100 0 300 500 200 6105 g23 v sense = 0v r in = 100 a v = 50v/v t a = C 40c t a = 25c t a = 85c t a = 125c v s + input voltage (v) 0 supply current (a) 300 350 35 250 200 10 20 5 15 25 40 30 45 50 0 150 400 100 6105 g24 v + = 3v v sense = 0v r in = 100 t a = C 40c t a = 25c t a = 85c t a = 125c supply current vs input voltage
LT6105 9 6105f 50s/div v s C 100mv/div 12v 0v v out 500mv/div 6105 g29 v + = 12v r in = 1k r out = 10k a v = 10v/v 50s/div v s C 100mv/div 0v 0v v out 500mv/div 6105 g30 v + = 12v r in = 1k r out = 10k a v = 10v/v 50s/div v s C 100mv/div 12v 0v v out 2v/div 6105 g31 v + = 12v v s + = 12v a v = 50v/ v 5s/div 0v 6105 g33 v + = 12v v s + = 12v r in = 1k r out = 50k a v = 50v/ v v s C 100mv/div 11.995v v out 5v 2v/div 5s/div v s C 100mv/div 12v 0v v out 2v/div 6105 g32 v + = 12v v s + = 12v r in = 1k r out = 50k a v = 50v/ v 5v step response v sense = 0v to 100mv, v s + = 12v typical performance characteristics step response v sense = 0v to 100mv, v s + = 0v step response v sense = 0v to 100mv, r in = 100 step response v sense = 5mv to 100mv step response v sense = 0v to 100mv gain vs frequency common mode rejection ratio vs frequency frequency (hz) C10 gain (db) 10 30 1k 100k 1m 10m C40 C30 10k 40 0 20 C20 6105 g25 v + = v s + = 12v v sense = 50mv r in = 100 a v = 10v/v frequency (hz) 60 common mode rejection ratio (db) 100 100 100k 1m 10m 0 20 1k 10k 140 80 120 40 6105 g26 v + = 12v v s + = 12v r in = 100 a v = 50v/v frequency (hz) power supply rejection ratio (db) 1 10 100 1k 10k 100k 1m 6105 g27 0.1 60 100 140 0 20 160 80 120 40 v + = 12v v sense = 5mv r in = 100 a v = 10v/v v s + = 0v v s + = 12v r in ( ) 0 slew rate (v/s) 1.5 2.0 2.5 800 1.0 0.5 0 100 200 300 400 500 600 700 900 1000 v + = 12v v s + = 12v v out = 7.5v a v = 50v/ v 6105 g28 Cslew rate +slew rate power supply rejection ratio vs frequency slew rate vs r in
LT6105 10 6105f 20s/div v + 0v 0v 5v v out 1v/div 6105 g41 v s + = 12v v sense = 100mv r in = 1k a v = 10v/ v 50s/div v s C 10mv/div 0v 0v v out 200v/div 6105 g40 v + = 12v r in = 100 r out = 5k a v = 50v/ v c l = 1000pf typical performance characteristics power supply start-up response 50s/div v s C 100mv/div 0v 0v v out 2v/div 6105 g39 v + = 12v r in = 100 r out = 5k a v = 50v/ v c l = 1000pf 50s/div v s C 10mv/div 12v 0v v out 200mv/div 6105 g38 v + = 12v r in = 100 r out = 5k a v = 50v/ v c l = 1000pf step response v sense = 0v to 10mv, v s + = 0v step response v sense = 0v to 100mv, c l = 1000pf, v s + = 12v 50s/div v s C 100mv/div 12v 0v v out 2v/div 6105 g37 v + = 12v r in = 100 r out = 5k a v = 50v/ v c l = 1000pf 50s/div v s C 10mv/div 0v 0v v out 200mv/div 6105 g36 v + = 12v r in = 100 r out = 5k a v = 50v/ v step response v sense = 0v to 10mv, v s + = 12v 50s/div v s C 10mv/div 12v 0v v out 200mv/div 6105 g35 v + = 12v r in = 100 r out = 5k a v = 50v/ v 5s/div 6105 g34 v + = 12v v s + = 12v r in = 1k r out = 50k a v = 50v/ v 0v v s C 100mv/div 11.995v v out 5v 2v/div step response v sense = 100mv to 5mv step response v sense = 0v to 10mv, c l = 1000pf, v s + = 12v step response v sense = 0v to 100mv, c l = 1000pf, v s + = 0v step response v sense = 0v to 10mv, c l = 1000pf, v s + = 0v
LT6105 11 6105f pin functions Cin (pin 1/pin 1): negative sense input terminal. negative sense voltage input will remain functional for voltages up to 44v, referred to v C . connect Cin to an external gain-setting resistor r in1 (r in1 = r in2 ) to set the gain. v + (pin 2/pin 2): power supply voltage. this pin supplies current to the ampli? er and can operate from 2.85v to 36v, independent of the voltages on the Cin or +in pins. v C (pin 3/pin 4): negative power supply voltage or ground for single supply operation. v out (pin 4/pin 5): voltage output: v out = a v ? (v sense v os ) v os is the input offset voltage. a v is the gain set by exter- nal r in1 , r in2 , r out . a v = r out /r in1 , for r in1 = r in2 . nc (pin 5/pins 3, 6, 7): not connected internally. +in (pin 6/pin 8): positive sense input terminal. connecting a source to v s + and a load to v s C will allow the LT6105 to monitor the current through r sense , refer to figure 1. connect +in to an external gain-setting resistor r in2 to set the gain. +in remains functional for voltages up to 44v, referred to v C . exposed pad (pin 7) dfn only: v C . the exposed pad is connected to the v C pin. it should be connected to the v C trace of the pcb, or left ? oating. (dcb/ms8) block diagram r out v sense r sense r in2 r in1 v s + v s C LT6105 to load source 0v to 44v v out = v sense ? r out r in2 v out = v sense ? where r in = r in1 = r in2 r out r in a v = r out r in v out v + Cin +in v C set r in1 = r in2 for best accuracy if r in1 r in2 , then r in1 , r in2 , r out are external resistors v (Cin) > 1.6v: v out = v sense ? r out r in1 v (Cin) < 1.6v: 6105 f01 C + C + a1 q2 q3 q1 a2 figure 1. simpli? ed block diagram
LT6105 12 6105f the LT6105 extended input range current sense am- pli? er (see figure 1) provides accurate unidirectional monitoring of current through a user-selected sense resis- tor. the LT6105 is fully speci? ed over a C0.3v to 44v input common mode range. a high psrr v + supply (2.85v to 36v) powers the current sense ampli? er. the input sense voltage is level shifted from the sensed power supply to the ground reference and ampli? ed by a user-selected gain to the output. the output voltage is directly proportional to the current ? owing through the sense resistor. theory of operation (refer to figure 1) case 1: high input voltage (1.6v < v Cin < 44v) current from the source at v s + ? ows through r sense to the load at v s C , creating a sense voltage, v sense . inputs v s + and v s C apply the sense voltage to r in2 . the opposite ends of resistors r in1 and r in2 are forced to be at equal potentials by the voltage gain of ampli? er a2. thus, the current through r in2 is v sense /r in2 . the current through r in2 is forced to ? ow through transistor q1 and into r out , creating an output voltage, v out . under this input operation range, ampli? er a1 is kept off. the base current of q1 has been compensated for and will not contribute to output error. the current from r in2 ? owing through resistor r out gives an output voltage of v out = v sense ? r out /r in2 , producing a gain voltage of a v = v out /v sense = r out /r in2 . case 2: low input voltage (0v < v Cin < 1.6v) current from the source at v s + ? ows through r sense to the load at v s C , creating a sense voltage, v sense . inputs v s + and v s C apply the sense voltage to r in1 . the opposite ends of resistors r in1 and r in2 are forced to be at equal potentials by the voltage gain of ampli? er a1. thus, the collector current of q3 will ? ow out of the Cin pin through r in1 . q2 mirrors this current v sense /r in1 to r out , creat- ing an output voltage, v out . under this input operation range, ampli? er a2 is kept off. this current v sense /r in1 ? owing through resistor r out gives an output voltage of v out = v sense ? r out /r in1 , producing a gain voltage of a v = v out /v sense = r out /r in1 . applications information selection of external current sense resistor external r sense resistor selection is a delicate trade-off between power dissipation in the resistor and current measurement accuracy. for high current applications, the user may want to minimize the sense voltage to minimize the power dissipation in the sense resistor. the system load current will cause both heat and voltage loss in r sense . as a result, the sense resistor should be as small as possible while still providing the input dynamic range required by the measurement. note that input dy- namic range is the difference between the maximum input signal and the minimum accurately reproduced signal, and is limited primarily by input dc offset voltage of the internal ampli? er of the LT6105. the sense resistor value will be set from the minimum signal current that can be accurately resolved by this sense amp. as an example, the LT6105 has a typical input offset of 100v. if the minimum current is 20ma, a sense resistor of 5m will set v sense to 100v, which is the same value as the input offset. a larger sense resistor will reduce the error due to offset by increasing the sense voltage for a given load current, but it will limit the maximum peak current for a given application. for a peak current of 2a and a maximum v sense of 80mv, r sense should not be more than 40m . the input offset causes an error equivalent to only 2.5ma of load current. peak dissipation is 160mw. if a 20m sense resistor is employed, then the effective current error is 5ma, while the peak sense voltage is reduced to 40mv at 2a, dis- sipating only 80mw. the LT6105s low input offset voltage of 100v allows for high resolution while limiting the maximum sense voltages. coupled with full scale sense voltage as large as 1v for r in = 1k, it can achieve 80db of dynamic range. sense resistor connection kelvin connection of the LT6105s input resistors to the sense resistor should be implemented to provide the high- est accuracy in high current applications. solder connec- tions and pc board interconnect resistance (approximately 0.5m per square for 1oz copper) can be a large error in high current systems. a 5a application might choose
LT6105 13 6105f a 20m sense resistor to give a 100mv full-scale input to the LT6105. input offset voltage will limit resolution to 5ma. neglecting contact resistance at solder joints, even one square of pc board copper at each resistor end will cause an error of 5%. this error will grow proportionately higher as monitored current levels rise. gain setting the gain is set with three external resistors, r in1 , r in2 , r out . the gain, r out /r in , selected can range from 1v/v to 100v/v as long as the maximum current does not exceed 1ma. select gain = r out /r in2 for sense input voltage op- eration greater than 1.6v. select gain = r out /r in1 for sense input voltage operation less than 1.6v. the overall system error will depend on the resistor tolerance chosen for the application. set r in1 = r in2 for best accuracy across the entire input range. the total error will be gain error of the resistors plus the gain error of the LT6105 device. output signal range the LT6105s output signal is developed by current through r in2 (44v > v Cin > 1.6v) or r in1 (0v < v Cin < 1.6v) conducted to the output resistor, r out . this current is v sense /r in2 or v sense /r in1 . the sense ampli? ers maxi- mum output current before gain error begins to increase applications information is 1ma. this allows low value output resistors to be used which helps preserve signal accuracy when the output pin is connected to other systems. for zero v sense , the internal circuitry gain will force v out to v o(min) referred to v C . depending on output currents, v out may swing positive to within v o(max) referred to v + or a maximum of 36v, a limit set by internal junction break- down. within these constraints, an ampli? ed, level shifted representation of r sense voltage is developed at v out . the output is well behaved driving capacitive loads. cm input signal range the LT6105 has high cmrr over the full input voltage range. the minimum operation voltage of the sense ampli- ? er inputs is 0v whether v + is at 2.7v or 36v. the output remains accurate even when the sense inputs are driven to 44v. the graph in figure 2 shows that v os changes very slightly over a wide input range. furthermore, either sense inputs v s + and v s C can collapse to 0v without incurring any damage to the device. the LT6105 can handle differential sense voltages up to 44v. for example, v s + = 44v and v s C = 0v can be a valid condition in a current monitoring applica- tion (figure 3) when an overload protection fuse is blown and v s C voltage collapses to ground. under this condition, the output of the LT6105 goes to the positive rail, v o(max) . figure 2. input offset voltage vs v s + input voltage figure 3. current monitoring of a fuse protected circuit output out 6105 f03 r sense fuse LT6105 v s C v s + v C v + c2 0.1 m f c1 0.1 m f dc source ( 44v) 5v to load C + + Cin +in r in2 r out r in1 v s + input voltage (v) 0 input offset voltage (mv) 0.20 0.40 0.60 35 0 C0.20 10 20 5 15 25 40 30 45 C0.80 C1.00 C0.40 0.80 C0.60 6105 f02 t a = C 40c t a = 25c t a = 85c t a = 125c v + = 12v v sense = 5mv a v = 50v/v
LT6105 14 6105f there is no phase inversion. for the opposite case, when v s + collapses to ground with v s C held up at some higher voltage potential, the output will sit at v o(min) . the two input stages crossover region the wide common mode input range is achieved with two input stages. these two input stages consist of a pair of matched common base pnp input transistors and a pair of common emitter pnp input transistors. as result of two input stages, there will be three distinct operating regions around the transition region as shown in the input bias current vs sense input voltage curve in the typical performance characteristics section. the crossover voltage, the voltage where the g m of one input stage is transferred to the other, occurs at 1.6v above v C . near this region, one input stage is shutting off while the other is turning on. increases in temperature will cause the crossover voltage to decrease. for input operation between 1.6v and 44v, the common base pnps are active (q2, q3 of figure 1). the typical current through each input at v sense = 0v is 15a. the input offset voltage is 300v maximum at room temperature. for input operation between 1.6v to 0v, the other pnp is active. the current out of the inputs at v sense = 0v is 100na. the input offset voltage is untrimmed and is typically 300v. selection of external output resistor, r out the output resistor, r out , determines how the output cur- rent is converted to voltage. v out is simply i rin ? r out . in choosing an output resistor, the maximum output volt- age must ? rst be considered. if the following circuit is a buffer or adc with limited input range, then r out must be chosen so that i out(max) ? r out is less than the allowed maximum input range of this circuit. in addition, the output impedance is determined by r out . if the circuit to be driven has high input impedance, then almost any useful output impedance will be acceptable. however, if the driven circuit has relatively low input imped- ance, or draws spikes of current such as an adc might do, then a lower r out value may be required in order to preserve the accuracy of the output. as an example, if the input impedance of the driven circuit is 100 times r out , then the accuracy of v out will be reduced by 1% since: vi rr rr out out out in driven out in driven = + = ? ? () () i ir ir out out out out ?? .?? 100 101 099 = full-scale sense voltage, selection of external input resistor, r in the external input resistor, r in , controls the transconduc- tance of the current sense circuit. since i out = v sense /r in , transconductance g m = 1/r in . for example, if r in =100, then i out = v sense /100 or i out = 1ma for v sense =100mv. r in should be chosen to allow the required resolution while limiting the output current. the LT6105 can output more than 1ma into r out without introducing a signi? - cant increase in gain error. by setting r in such that the largest expected sense voltage gives i out = 1ma, then the maximum output dynamic range is available. output dynamic range is limited by both the maximum allowed output current and the maximum allowed output voltage, as well as the minimum practical output signal. if less dynamic range is required, then r in can be increased accordingly, reducing the maximum output current and power dissipation. the LT6105s performance is optimized for values of r in = 100 to 1k. values outside this range may result in additional errors. the power dissipation across r in and r out should not exceed the resistors recommended ratings. applications information
LT6105 15 6105f error sources the current sense system uses an ampli? er, current mirrors and external resistors to apply gain and level shifting. the output is then dependent on the matching characteristics of the current mirrors, characteristics of the ampli? er such as gain and input offset, as well as matching of external resistors. ideally, the circuit output is: vv r r vir out sense out in sense sense sense == ?; ? in this case, the only error is due to resistor mismatch, which provides an error in gain only. mismatch in the internal current mirror adds to gain error but is trimmed to less than 0.3%. offset voltage and sense input current are the main cause of any additional error. error due to input offset voltage dynamic range is inversely proportional to the input offset voltage. dynamic range can be thought of as the maximum v sense divided by v os . the offset voltage of the LT6105 is typically only 100v. error due to sense input offset current input offset current or mismatches in input bias current will introduce an additional input offset voltage term. typical input offset current is 0.05a. lower values of r in will keep this error to a minimum. for example, if r in = 100, then the additional offset is 5v. output current limitations due to power dissipation the LT6105 can deliver up to 1ma continuous current to the output pin. this output current, i out , is the mirrored current which ? ows through r in2 and enters the current sense amp via the +in pin for v Cin > 1.6v, and exits out of Cin through r in1 for v Cin < 1.6v. the total power dissipa- tion due to input currents, p in , and the dissipation due to internal mirrored currents, p q : p total = p in + p q p in = (v +in ) ? i rin2 ; v Cin > 1.6v or p in = (v + C (v Cin )) ? i rin1 ; v Cin < 1.6v since the current exiting Cin is coming from v + , the voltage is v + C v Cin . taking the worst case v Cin = 0v, the above equation becomes: p in ? v + ? i rin1 , for v Cin < 1.6v. the power dissipated due to internal mirrored currents: p q = 2 ? i out ? v + the factor of 2 is the result of internal current shifting and 1:1 mirroring. at maximum supply and maximum output current, the total power dissipation can exceed 100mw. this will cause signi? cant heating of the LT6105 die. in order to prevent damage to the LT6105, the maximum expected dissipation in each application should be calculated. this number can be multiplied by the ja value listed in the pin con? guration section to ? nd the maximum expected die temperature. this must not be allowed to exceed 150c, or performance may be degraded. as an example, if an LT6105 in the msop package is to be run at v s + = 44v and v + = 36v with 1ma output current at 80c ambient: p q(max) = 2 ? i out(max) ? v + = p q(max) = 72mw p in(max) = i rin2(max) ? v +in(max) = 44mw t rise = ja ? p total(max) t max = t ambient + t rise t max must be < 150c p total(max) = 116mw and the maximum die temperature will be 109c. if this same circuit must run at 125c ambi- ent, the maximum die temperature will increase to 150c. note that supply current, and therefore p q , is proportional to temperature. refer to the typical performance charac- teristics section. in this condition, the maximum output current should be reduced to avoid device damage. the dcb package, on the other hand, has a lower ja and subsequently, a lower die temperature increase than the msop . with the same condition as above, the dcb will rise only 7.5c to 87.5c and 132.5c, respectively. it is important to note that the LT6105 has been designed to provide at least 1ma to the output when required, and can deliver more under large v sense conditions. care must be taken to limit the maximum output current by proper choice of sense resistor and input resistors. applications information
LT6105 16 6105f output filtering the output voltage, v out is simply i out ? z out . this makes ? ltering straightforward. any circuit may be used which generates the required z out to get the desired ? lter response. for example, a capacitor in parallel with r out will give a low pass response. this will reduce unwanted noise from the output, and may also be useful as a charge reservoir to keep the output steady while driving a switch- ing circuit such as a mux or an adc. this output capacitor in parallel with an output resistor will create a pole in the output response at: f rc db out out ? ?? ? 3 1 2 = applications information response time the LT6105 is designed to exhibit fast response to inputs for the purpose of circuit protection or signal transmission. this response time will be affected by the external circuit in two waysdelay and speed. if the output current is very low and an input transient occurs, there may be an increased delay before the output voltage begins changing. this can be improved by increasing the minimum output current, either by increasing r sense or decreasing r in . the effect of increased output current is illustrated in the step response curves in the typical performance characteristics section of this data sheet. note that the curves are labeled with respect to the initial output currents. the speed is also affected by the external circuit. in this case, if the input changes very quickly, the internal ampli? er will slew the base of the internal output pnp (figure 1) in order to maintain the internal loop. this results in current ? owing through r in and the internal pnp . this current slew rate will be determined by the ampli? er and pnp characteris- tics as well as the input resistor, r in . see the slew rate vs r in curve in the typical performance characteristics section. using a smaller r in will allow the output current to increase more quickly, decreasing the response time at the output. this will also have the effect of increasing the maximum output current. C + 0.039 249 249 4.99k LT6105 to load source 0v to 44v v out = 780mv/a v out 0.22f 6105 ta02 2.85v to 36v v s + v s C Cin +in v C v + gain of 20 current sense ampli? er with output filtering typical applications
LT6105 17 6105f typical applications 50ms/div 5v/div 2v/div 10v/div 6105 f05 v bat = 3.6v i cpo = 200a c cpo = 2.2f figure 5. current measurement waveforms. the top trace is the mosfet gate with high on. the middle trace is the bottom of the solenoid/ inductor. the bottom trace is the LT6105 output, representing solenoid current at 80ma / div. glitches are useful indicators of solenoid plunger movement solenoid monitor the large input common mode range of the LT6105 makes it suitable for monitoring currents in quarter, half and full bridge inductive load driving applications. figure 4 shows an example of a quarter bridge. the mosfet pulls down on the bottom of the solenoid to increase solenoid current. it lets go to decrease current, and the solenoid voltage freewheels around the schottky diode. current measurement waveforms are shown in figure 5. the small glitches occur due to the action of the solenoid plunger, and this provides an opportunity for mechanical system monitoring without an independent sensor or limit switch. figure 6 shows another solenoid driver circuit, this time with one end of the solenoid grounded and a p-channel mosfet pulling up on the other end. in this case, the inductor freewheels around ground, imposing a negative input common mode voltage of one schottky diode drop. this voltage may exceed the input range of the LT6105. this does not endanger the device, but it severely degrades its accuracy. in order to avoid violating the input range, pull-up resistors may be used as shown. 6105 f04 LT6105 v C v + 24v, 3w solenoid 200 1% 1n5818 2n7000 Cin +in 4.99k 1% 200 1% v out = 25mv/ma v out 5v dc 24v dc 0v/off 5v/on C + 1 1% 6105 f06 LT6105 v C v + 2k 1% 2k 1% 24v, 3w solenoid 200 1% 1n5818 tp0610l 1n914 Cin +in 4.99k 1% 200 1% v out = 25mv/ma v out 5v dc 24v dc 19v/on 24v/off C + 1 1% figure 4. simplest form of a solenoid driver. the LT6105 monitors the current in both on and freewheel states. the lowest common mode voltage is 0v, while the highest is 24v plus the forward voltage of the schottky diode figure 6. a similar circuit to figure 4, but with solenoid grounded, so freewheeling forces inputs negative. providing resistive pull-ups keeps ampli? er inputs from falling outside of their accurate input range
LT6105 18 6105f package description 3.00 0.10 (2 sides) 2.00 0.10 (2 sides) note: 1. drawing to be made a jedec package outline m0-229 variation of (tbd) 2. drawing not to scale 3. all dimensions are in millimeters 4. dimensions of exposed pad on bottom of package do not include mold flash. mold flash, if present, shall not exceed 0.15mm on any side 5. exposed pad shall be solder plated 6. shaded area is only a reference for pin 1 location on the top and bottom of package 0.40 0.10 bottom view?exposed pad 1.65 0.10 (2 sides) 0.75 0.05 r = 0.115 typ r = 0.05 typ 1.35 0.10 (2 sides) 1 3 6 4 pin 1 bar top mark (see note 6) 0.200 ref 0.00 ? 0.05 (dcb6) dfn 0405 0.25 0.05 0.50 bsc pin 1 notch r0.20 or 0.25 45 chamfer 0.25 0.05 1.35 0.05 (2 sides) recommended solder pad pitch and dimensions 1.65 0.05 (2 sides) 2.15 0.05 0.70 0.05 3.55 0.05 package outline 0.50 bsc dcb package 6-lead plastic dfn (2mm 3mm) (reference ltc dwg # 05-08-1715)
LT6105 19 6105f information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no representa- tion that the interconnection of its circuits as described herein will not infringe on existing patent rights. package description msop (ms8) 0204 0.53 0.152 (.021 .006) seating plane note: 1. dimensions in millimeter/(inch) 2. drawing not to scale 3. dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.152mm (.006") per side 4. dimension does not include interlead flash or protrusions. interlead flash or protrusions shall not exceed 0.152mm (.006") per side 5. lead coplanarity (bottom of leads after forming) shall be 0.102mm (.004") max 0.18 (.007) 0.254 (.010) 1.10 (.043) max 0.22 ? 0.38 (.009 ? .015) typ 0.127 0.076 (.005 .003) 0.86 (.034) ref 0.65 (.0256) bsc 0 ? 6 typ detail ?a? detail ?a? gauge plane 12 3 4 4.90 0.152 (.193 .006) 8 7 6 5 3.00 0.102 (.118 .004) (note 3) 3.00 0.102 (.118 .004) (note 4) 0.52 (.0205) ref 5.23 (.206) min 3.20 ? 3.45 (.126 ? .136) 0.889 0.127 (.035 .005) recommended solder pad layout 0.42 0.038 (.0165 .0015) typ 0.65 (.0256) bsc ms8 package 8-lead plastic msop (reference ltc dwg # 05-08-1660)
LT6105 20 6105f linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax: (408) 434-0507 www.linear.com ? linear technology corporation 2007 lt 1207 ? printed in usa related parts typical application part number description comments lt1787/lt1787hv precision, bidirectional, high side current sense ampli? er 2.7v to 60v operation, 75v offset, 60a current draw ltc4150 coulomb counter/battery gas gauge indicates charge quantity and polarity lt6100 gain-selectable high side current sense ampli? er 4.1v to 48v operation, pin-selectable gain: 10v/v, 12.5v/v, 20v/v, 25v/v, 40v/v, 50v/v ltc6101/ ltc6101hv high voltage high side current sense ampli? er 4v to 60v/5v to 100v operation, external resistor set gain, sot23 ltc6102/ ltc6102hv zero drift high side current sense ampli? er 4v to 60v/5v to 100v operation, 10v offset, 1s step response, msop8 / dfn ltc6103 dual high side precision current sense ampli? er 4v to 60v, gain con? gurable, 8-pin msop ltc6104 bidirectional high side precision current sense ampli? er 4v to 60v, gain con? gurable, 8-pin msop lt6106 low cost, high side precision current sense ampli? er 2.7v to 36v, gain con? gurable, sot23 C + 6105 f07 LT6105 v C v + to C15v load C15v C15v negative supply 100 1% Cin +in 4.99k 1% 100 1% v out = 1v/a v out 5v dc C + 20m 1% current flow LT6105 v C v + to +15v load C15v +15v positive supply 100 1% Cin +in 4.99k 1% 100 1% v out = 1v/a v out 5v dc 20m 1% current flow figure 7. the LT6105 can monitor the current of either positive or negative supplies, without a schematic change. just ensure that the current flow is in the correct direction supply monitoring the input common mode range of the LT6105 also makes it suitable for monitoring either positive or negative sup- plies. figure 7 shows one LT6105 applied as a simple positive supply monitor, and another LT6105 as a simple negative supply monitor. note that the schematics are practically identical and both have outputs conveniently referred to ground. the only requirement for negative supply monitoring, in addition to the usual constraints of the absolute maximum ratings, is that the negative supply to that LT6105 be at least as negative as the supply it is monitoring.

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